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PDF AAT1145 Data sheet ( Hoja de datos )
| Número de pieza | AAT1145 | |
| Descripción | 1.2A Step-Down Converter | |
| Fabricantes | Advanced Analogic Technologies | |
| Logotipo |  |
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SwitchRegTM
General Description
The AAT1145 SwitchReg™ is a 1.5MHz constant fre-
quency current mode PWM step-down converter. It is
ideal for portable equipment requiring very high current
up to 1.2A from single-cell Lithium-ion batteries while
still achieving over 90% efficiency during peak load con-
ditions. The AAT1145 also can run at 100% duty cycle
for low dropout operation, extending battery life in por-
table systems while light load operation provides very
www.DatalSohweeot4uUt.pcoumt ripple for noise sensitive applications.
The AAT1145 can supply up to 1.2A output load current
from a 2.5V to 5.5V input voltage and the output voltage
can be regulated as low as 0.6V. The high switching fre-
quency minimizes the size of external components while
keeping switching losses low. The internal slope compen-
sation setting allows the device to operate with smaller
inductor values to optimize size and provide efficient
operation.
The AAT1145 is available in adjustable (0.6V to VIN) and
fixed (1.8V) output voltage versions. The device is avail-
able in a Pb-free, 3x3mm 10-lead TDFN package and is
rated over the -40°C to +85°C temperature range.
PRODUCT DATASHEET
AAT1145
1.2A Step-Down Converter
Features
• Input Voltage Range: 2.5V to 5.5V
• Output Voltages from 0.6V to VIN
• 1.2A Output Current
• High Efficiency: Up to 95%
• 1.5MHz Constant Switching Frequency
• Low RDS(ON) Internal Switches: 0.15Ω
• Allows Use of Ceramic Capacitors
• Current Mode Operation for Excellent Line and Load
Transient Response
• Short-Circuit and Thermal Fault Protection
• Soft Start
• Low Dropout Operation: 100% Duty Cycle
• Low Shutdown Current: ISHUTDOWN < 1μA
• TDFN33-10 Package
• -40°C to +85°C Temperature Range
Applications
• Cellular Phones
• Digital Cameras
• DSP Core Supplies
• PDAs
• Portable Instruments
• Smart Phones
Typical Application
VIN 2.5V-5.5V
C1
10μF
1 EN
2 IN
LX 8
LX 7
3 AIN AAT1145-1.8 OUT 5
6 AGND
4 AGND
PGND 10
PGND 9
L1
2.2μH
VOUT
1.8V,1.2A
C2
22μF
1145.2007.11.1.1
www.analogictech.com
1
1 page  
SwitchRegTM
Typical Characteristics
Efficiency vs. Output Current
(VOUT = 3.3V; TA = 25°C; L = 2.2µH)
100
90
80
70
60
50
www.DataSheet440U.com
30
20
10
0
0.1
VIN = 4.2V
VIN = 3.6V
1 10
VIN = 5.0V
100 1000
Output Current (mA)
10000
100
90
80
70
60
50
40
30
20
10
0
0.1
Efficiency vs. Output Current
(VOUT = 1.5V; TA = 25°C; L = 2.2µH)
VIN = 2.5V
VIN = 3.6V
VIN = 5.0V
VIN = 4.2V
1 10 100 1000
Output Current (mA)
10000
Output Voltage vs. Output Current
(VOUT = 3.3V; TA = 25°C; L = 2.2µH)
3.400
3.380
3.360
3.340
3.320
3.300
3.280
3.260
3.240
3.220
3.200
0
VIN = 3.6V
VIN = 5.0V
VIN = 4.2V
200 400 600 800 1000
1200
Output Current (mA)
PRODUCT DATASHEET
AAT1145
1.2A Step-Down Converter
Efficiency vs. Output Current
(VOUT = 1.8V; TA = 25°C; L = 2.2µH)
100
90
80
70
60
50
40
30
20
10
0
0.1
VIN = 3.6V
VIN = 2.5V
VIN = 5.0V
VIN = 4.2V
1 10 100
1000
Output Current (mA)
10000
100
90
80
70
60
50
40
30
20
10
0
0.1
Efficiency vs. Output Current
(VOUT = 1.2V; TA = 25°C; L = 2.2µH)
VIN = 2.5V
VIN = 3.6V
VIN = 5.0V
VIN = 4.2V
1 10 100 1000
Output Current (mA)
10000
Output Voltage vs. Output Current
(VOUT = 1.8V; TA = 25°C; L = 2.2µH)
1.820
1.815
1.810
1.805
1.800
VIN = 5.0V
VIN = 4.2V
1.795
1.790
VIN = 2.5V VIN = 3.6V
1.785
1.780
0
200
400
600
800
1000
1200
Output Current (mA)
1145.2007.11.1.1
www.analogictech.com
5
5 Page 
SwitchRegTM
The input capacitor RMS ripple current varies with the
input and output voltage and will always be less than or
equal to half of the total DC load current.
I =RMS(MAX)
1
2
· IO
To minimize stray inductance, the capacitor should be
placed as closely as possible to the IC. This keeps the
www.DataShhigehet4fUr.ecqomuency content of the input current localized,
minimizing EMI and input voltage ripple. The proper
placement of the input capacitor (C1) can be seen in the
evaluation board layout in Figures 3 and 4.
A laboratory test set-up typically consists of two long
wires running from the bench power supply to the eval-
uation board input voltage pins. The inductance of these
wires, along with the low-ESR ceramic input capacitor,
can create a high Q network that may affect converter
performance. This problem often becomes apparent in
the form of excessive ringing in the output voltage dur-
ing load transients. Errors in the loop phase and gain
measurements can also result.
Since the inductance of a short PCB trace feeding the
input voltage is significantly lower than the power leads
from the bench power supply, most applications do not
exhibit this problem.
In applications where the input power source lead induc-
tance cannot be reduced to a level that does not affect
the converter performance, a high ESR tantalum or alu-
minum electrolytic should be placed in parallel with the
low ESR, ESL bypass ceramic. This dampens the high Q
network and stabilizes the system.
Output Capacitor Selection
The function of output capacitance is to store energy to
attempt to maintain a constant voltage. The energy is
stored in the capacitor’s electric field due to the voltage
applied.
The value of output capacitance is generally selected to
limit output voltage ripple to the level required by the
specification. Since the ripple current in the output induc-
tor is usually determined by L, VOUT and VIN, the series
impedance of the capacitor primarily determines the out-
put voltage ripple. The three elements of the capacitor
that contribute to its impedance (and output voltage
PRODUCT DATASHEET
AAT1145
1.2A Step-Down Converter
ripple) are equivalent series resistance (ESR), equivalent
series inductance (ESL), and capacitance (C).
The output voltage droop due to a load transient is
dominated by the capacitance of the ceramic output
capacitor. During a step increase in load current, the
ceramic output capacitor alone supplies the load current
until the loop responds. Within two switching cycles, the
loop responds and the inductor current increases to
match the load current demand. The relationship of the
output voltage droop during the two switching cycles to
the output capacitance can be estimated by:
COUT =
2 · ΔILOAD
VDROOP · fS
In many practical designs, to get the required ESR, a
capacitor with much more capacitance than is needed
must be selected.
For both continuous or discontinuous inductor current
mode operation, the ESR of the COUT needed to limit the
ripple to ∆VO, V peak-to-peak is:
ESR ≤
ΔVO
ΔIL
Ripple current flowing through a capacitor’s ESR causes
power dissipation in the capacitor. This power dissipation
causes a temperature increase internal to the capacitor.
Excessive temperature can seriously shorten the expect-
ed life of a capacitor. Capacitors have ripple current rat-
ings that are dependent on ambient temperature and
should not be exceeded. The output capacitor ripple cur-
rent is the inductor current, IL, minus the output current,
IO. The RMS value of the ripple current flowing in the
output capacitance (continuous inductor current mode
operation) is given by:
IRMS = ΔIL ·
3
6
= ΔIL · 0.289
ESL can be a problem by causing ringing in the low
megahertz region but can be controlled by choosing low
ESL capacitors, limiting lead length (PCB and capacitor),
and replacing one large device with several smaller ones
connected in parallel.
1145.2007.11.1.1
www.analogictech.com
11
11 Page | ||
| Páginas | Total 16 Páginas | |
| PDF Descargar | [ Datasheet AAT1145.PDF ] | |
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