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ADP1610 Schematic ( PDF Datasheet ) - Analog Devices

Teilenummer ADP1610
Beschreibung 1.2 MHz DC-DC Step-Up Switching Converter
Hersteller Analog Devices
Logo Analog Devices Logo 




Gesamt 16 Seiten
ADP1610 Datasheet, Funktion
www.DataSheet4U.com
1.2 MHz DC-DC Step-Up Switching Converter
ADP1610
FEATURES
Fully integrated 1.2 A , 0.2 Ω, power switch
Pin-selectable 700 kHz or 1.2 MHz PWM frequency
92% efficiency
Adjustable output voltage up to 12 V
3% output regulation accuracy
Adjustable soft start
Input undervoltage lockout
MSOP 8-lead package
APPLICATIONS
TFT LC bias supplies
Portable applications
Industrial/instrumentation equipment
GENERAL DESCRIPTION
The ADP1610 is a dc-to-dc step-up switching converter with an
integrated 1.2 A, 0.2 Ω power switch capable of providing an
output voltage as high as 12 V. With a package height of less that
1.1 mm, the ADP1610 is optimal for space-constrained
applications such as portable devices or thin film transistor
(TFT) liquid crystal displays (LCDs).
The ADP1610 operates in pulse-width modulation (PWM)
current mode with up to 92% efficiency. Adjustable soft start
prevents inrush currents at startup. The pin-selectable switching
frequency and PWM current-mode architecture allow excellent
transient response, easy noise filtering, and the use of small,
cost-saving external inductors and capacitors.
The ADP1610 is offered in the Pb-free 8-lead MSOP and
operates over the temperature range of −40°C to +85°C.
FB 2
RT 7
FUNCTIONAL BLOCK DIAGRAM
REF
COMP
1
ERROR
AMP
gm
IN
6
BIAS
ADP1610
RAMP
GEN
OSC
F/F
RQ
S
COMPARATOR
DRIVER
5 SW
SS 8
SD 3
SOFT START
Figure 1.
CURRENT
SENSE
AMPLIFIER
4
GND
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.326.8703 © 2004 Analog Devices, Inc. All rights reserved.






ADP1610 Datasheet, Funktion
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ADP1610
TYPICAL PERFORMANCE CHARACTERISTICS
100
VOUT = 10V
90 FSW = 700kHz
L = 10µH
80
70
VIN = 5.5V
VIN = 3.3V
VIN = 2.5V
60
50
40
30
20
10
0
1 10 100 1000
LOAD CURRENT (mA)
Figure 4. Output Efficiency vs. Load Current
100
VOUT = 10V
90 F = 1.2MHz
L = 4.7µH
80
70
VIN = 5.5V
VIN = 3.3V
VIN = 2.5V
60
50
40
30
20
10
0
1 10 100 1000
LOAD CURRENT (mA)
Figure 5. Output Efficiency vs. Load Current
100
VOUT = 7.5V
FSW = 700kHz
90 L = 10µH
80
VIN = 5.5V
VIN = 3.3V
VIN = 2.5V
70
60
50
40
30
1 10 100
LOAD CURRENT (mA)
Figure 6. Output Efficiency vs. Load Current
1000
100
VOUT = 7.5V
FSW = 1.2MHz
90 L = 4.7µH
80
VIN = 5.5V
VIN = 3.3V
VIN = 2.5V
70
60
50
40
30
1 10 100
LOAD CURRENT (mA)
Figure 7. Output Efficiency vs. Load Current
1000
2.4
2.2 VIN = 5.5V
2.0 VIN = 3.3V
1.8
VIN = 2.5V
1.6
1.4
1.2
–40
–15 10 35 60
AMBIENT TEMPERATURE (°C)
85
Figure 8. Current Limit vs. Ambient Temperature, VOUT = 10 V
1.4
1.2
RT = VIN
1.0
0.8
0.6 RT = GND
0.4
0.2 VOUT = 10V
VIN = 3.3V
0
–40 –15
10
35
60
AMBIENT TEMPERATURE (°C)
85
Figure 9. Oscillatory Frequency vs. Ambient Temperature
Rev. 0 | Page 6 of 16

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ADP1610 pdf, datenblatt
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ADP1610
DIODE SELECTION
The output rectifier conducts the inductor current to the output
capacitor and load while the switch is off. For high efficiency,
minimize the forward voltage drop of the diode. For this reason,
Schottky rectifiers are recommended. However, for high voltage,
high temperature applications, where the Schottky rectifier
reverse leakage current becomes significant and can degrade
efficiency, use an ultrafast junction diode.
Make sure that the diode is rated to handle the average output
load current. Many diode manufacturers derate the current
capability of the diode as a function of the duty cycle. Verify
that the output diode is rated to handle the average output load
current with the minimum duty cycle. The minimum duty cycle
of the ADP1610 is
D MIN
=
VOUT VIN MAX
VOUT
(12)
where VIN-MAX is the maximum input voltage.
Table 6. Schottky Diode Manufacturers
Vendor
Phone No.
Motorola
602-244-3576
Diodes, Inc.
805-446-4800
Sanyo
310-322-3331
Web Address
www.mot.com
www.diodes.com
www.irf.com
LOOP COMPENSATION
The ADP1610 uses external components to compensate the
regulator loop, allowing optimization of the loop dynamics for a
given application.
The step-up converter produces an undesirable right-half plane
zero in the regulation feedback loop. This requires compensat-
ing the regulator such that the crossover frequency occurs well
below the frequency of the right-half plane zero. The right-half
plane zero is determined by the following equation:
FZ
(RHP)
=
⎜⎜⎝⎛
VIN
VOUT
⎟⎟⎠⎞ 2
×
RLOAD
2π× L
(13)
where:
FZ(RHP) is the right-half plane zero.
RLOAD is the equivalent load resistance or the output voltage
divided by the load current.
To stabilize the regulator, make sure that the regulator crossover
frequency is less than or equal to one-fifth of the right-half
plane zero and less than or equal to one-fifteenth of the
switching frequency.
The regulator loop gain is
AVL
= VFB
VOUT
× VIN
VOUT
× G MEA ×
Z COMP
× GCS ×
Z OUT
(14)
where:
AVL is the loop gain.
VFB is the feedback regulation voltage, 1.230 V.
VOUT is the regulated output voltage.
VIN is the input voltage.
GMEA is the error amplifier transconductance gain.
ZCOMP is the impedance of the series RC network from COMP to
GND.
GCS is the current sense transconductance gain (the inductor
current divided by the voltage at COMP), which is internally set
by the ADP1610.
ZOUT is the impedance of the load and output capacitor.
To determine the crossover frequency, it is important to note
that, at that frequency, the compensation impedance (ZCOMP) is
dominated by the resistor, and the output impedance (ZOUT) is
dominated by the impedance of the output capacitor. So, when
solving for the crossover frequency, the equation (by definition
of the crossover frequency) is simplified to
|
AVL
|
=
VFB
VOUT
× VIN
VOUT
×
1
GMEA× RCOMP× GCS × 2π × fC ×COUT
=1
(15)
where:
fC is the crossover frequency.
RCOMP is the compensation resistor.
Solving for RCOMP,
R
=COMP
2π × f C ×COUT × VOUT × VOUT
VFB × VIN × GMEA × GCS
(16)
For VFB = 1.23, GMEA = 100 µS, and GCS = 2 S,
RCOMP
=
2.55 ×104
×
fC
× COUT
VIN
× VOUT
× VOUT
(17)
Once the compensation resistor is known, set the zero formed
by the compensation capacitor and resistor to one-fourth of the
crossover frequency, or
CCOMP
=
π×
fC
2
× RCOMP
(18)
where CCOMP is the compensation capacitor.
Rev. 0 | Page 12 of 16

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